Improved performance of circularly polarized antenna using semi-planar chiral metamaterial covers.
Recently, metamaterials (MTMs) exhibiting interesting and unique properties nonexistent in natural materials have attracted increasing attention. The early prominent MTM structures had negative index of refraction. Remarkably, the negative index MTMs can be achieved by both negative permittivity and negative permeability in the same spectral region, which show the best performance, i.e., lower losses. Many applications have been proposed for MTMs, such as the interesting applications in antenna structures for miniaturization [1-4], bandwidth enhancement and directive emission [5-13]. An attractive category of MTMs known as the zero-index materials exhibit a considerable influence on the wave propagation and in increasing the directivity of dipole, linearly polarized microstrip, and linearly polarized horn antennas .
In 2003, the possibility of realizing negative refraction by chiral nihility was discussed . In fact, chiral nihility is a special case of chiral media which several applications have been proposed for it [16-23]. Afterwards, the general conditions to realize negative refraction chiral metamaterials (CMMs) were investigated and it was shown that negative refraction can be realized in CMMs having strong chirality, with neither negative permittivity nor permeability . Although, natural chiral materials have very weak chirality, but properly designed CMM structures with considerable chirality can realize negative refractive index for either right circularly polarized (RCP) or left circularly polarized (LCP) waves. This property is the most manifest difference between CMMs and double-negative MTMs exhibiting negative refractive indices for linearly polarized waves. Recently, several theoretical [25,26] and experimental studies on CMMs and their interesting applications have been proposed, such as negative refraction index [27-33], ultrathin linear polarization rotators [27-34], circular polarizer , focusing of electromagnetic waves [36-38], wide angle and polarization independent absorbers , and cloaking [40, 41].
This paper presents gain enhancement and axial ratio (AR) improvement techniques for circularly polarized (CP) antennas based on the utilization of semi-planar CMM covers as a novel application of CMM structures.
2. CHIRAL METAMATERIAL STRUCTURES
The constitutive equations for chiral media assuming a time harmonic dependence [e.sup.-j[omega]t] are given by [42,43]:
D = [epsilon][[epsilon].sub.0]E + j[kappa][square root of [[epsilon].sub.0][[mu].sub.0]]H, B = -j[kappa][square root of [[epsilon].sub.0][[mu].sub.0]]E + [mu][[mu].sub.0]H (1)
where [[epsilon].sub.0] and [[mu].sub.0] are the permittivity and permeability of vacuum, and [epsilon] and [mu] are the relative permittivity and permeability of the chiral medium, and [kappa] is the so-called chirality parameter. With this extraordinary constitutive relationship, chiral media have two important properties. The first one is optical (or electromagnetic) activity, which can rotate the polarization plane of a linearly polarized wave propagating through it. The second property is circular dichroism, which is attributed to the different absorptivity of a RCP and LCP polarized wave inside chiral medium. The wave equation in an isotropic chiral medium is:
[[nabla].sup.2]E + 2 [kappa][omega] / [c.sub.0] [nabla] x E + [[omega].sup.2] / [c.sup.2.sub.0] ([mu][epsilon] - [[kappa].sup.2])E = 0 (2)
where [c.sub.0] and [omega] are the speed of light in vacuum and the angular frequency, respectively. It can be seen that the RCP and LCP waves are the eigenpolarization of the wave equation. The refractive indices for the RCP (+) and LCP (-) waves are :
[n.sub.[+ or -]] = n [+ or -] [kappa] (3)
where n = [square root of [epsilon][mu]]. Both RCP and LCP waves have the same impedance given by z / [z.sub.0] = [square root of [mu] / [epsilon] where [z.sub.0] is the impedance of free space. Given a large enough chirality, the negativity of refractive index for one of the circularly polarized wave is possible. Based on this concept, several semi-planar CMM structures have been proposed and demonstrated to achieve strong optical activity, circular dichroism, and negative refractive index, such as twisted rosettes , twisted crosses , twisted U-shaped Split Ring Resonators (U-SRRs) , double layer CMM structure , conjugated gammadion , complementary CMM structure , and L-shaped resonators CMM structure .
The four-fold rotational symmetry and lack of any mirror symmetry are inherent properties of aforementioned designs consisting of multiple layers of twisted copper patterns printed on dielectric boards. Owing to the missing four-fold rotational symmetry and linear birefringence, no optical activity is observable. Therefore, in order to obtain pure optical activity both chiral symmetry and four-fold rotational symmetry have to be present.
The parameter retrieval process of macroscopic electromagnetic (EM) parameters for a semi-planar CMM is generally the same as regular MTMs. However, due to the chiral nature of medium and different interactions among its chiral particles and RCP and LCP waves, it is somewhat more complicated . In fact, the circularly polarized transmission coefficients ([T.sub.[+ or -]]), and reflection coefficients ([R.sub.[+ or -]]) of RCP and LCP waves should be measured. For simplicity, a linearly polarized EM wave (first, electric field in the x and then in the y direction) is incident on the CMM structure and the linear transmission coefficients, [T.sub.xx], [T.sub.yx], [T.sub.yy], and [T.sub.xy], and the linear reflections, [R.sub.xx], [R.sub.yx], [R.sub.yy], and [R.sub.xy], are measured, where the first subscript indicates the transmitted (reflected) field polarization (x- or y-polarized), and the second indicates the incident field polarization. Then, the linearly polarized transmissions and reflections should be converted to circular transmission coefficients ([T.sub.++], [T.sub.+-], [T.sub.-+], [T.sub.--]) and reflection coefficients ([R.sub.++], [R.sub.+-], [R.sub.-+], [R.sub.--]), where the first subscript indicates the transmitted (reflected) field polarization (RCP or LCP), and the second indicates the incident field polarization. Consider the RCP and LCP plane waves with unity amplitude, [E.sup[+ or -]] = (1/2)[E.sub.0]([??][- or +]j[??]), and defining the linear and circular transmission matrices as:
[MATHEMATICAL EXPRESSION NOT REPRODUCIBLE IN ASCII] (4)
where i and t subscripts indicate the incident and transmitted waves, respectively. Then, it can be easily shown that the circular scattering coefficients are converted from the linear scattering coefficients using the following equation:
[MATHEMATICAL EXPRESSION NOT REPRODUCIBLE IN ASCII] (5)
where T can be also replaced with R.
[FIGURE 1 OMITTED]
3. TWO-ARM ARCHIMEDEAN SPIRAL ANTENNA WITH TWISTED CROSSES CMM COVER
3.1. Antenna Design
The configuration of the two-arm Archimedean spiral (ARSPL) antenna is shown in Figure 1(a). The radial distance from the origin to a point on each arm of the antenna is :
[MATHEMATICAL EXPRESSION NOT REPRODUCIBLE IN ASCII] (6)
where [a.sub.AR] = 1.273, [[PHI].sub.st] = 0.5[pi], [[PHI].sub.end] = 8.5[pi], w = 2 mm. In order to obtain a unidirectional beam, a metallic cavity with dimensions of 75 mm x 75 mm x 7 mm is placed at the back of ARSPL antenna as shown in Figure 1(b). However, this cavity deteriorates the radiation characteristics of antenna, which may be improved by an absorber strip (ABS) with [[epsilon].sub.r] = 1.1, [sigma] = 0.1 S/m, and internal radius of 29 mm and height of 7 mm attached to the vertical walls of the cavity (is not shown in figure).
[FIGURE 2 OMITTED]
3.2. Twisted Crosses CMM Cover
The design of bilayer cross-wires or twisted crosses as semi-planar CMM structure is already published . The unit cell of this CMM structure is constructed by two copper cross-wires with width [w.sub.0] = 0.7 mm and length l = 14 mm printed on the opposite sides of an FR-4 board with dielectric constant 4.5, dielectric loss tangent 0.025, and thickness t = 1.6 mm, as shown in Figure 2(a). Numerical simulations are executed in a frequency range of 2 to 12 GHz by using the unit cell template and frequency domain solver of CST Microwave Studio. Using a standard parameter retrieval method , the real and imaginary parts of [n.sub.[+ or -]] are calculated and illustrated in Figure 3. According to these results and the near zero real and imaginary parts of [n.sub.+], it is expected that the application of this semi-planar CMM structure as a cover for a RCP antenna at frequency of about 6.7 GHz, the antenna directivity increases significantly due to the focusing effect. Note that these retrieved results are valid for a very large cover consisting of many unit cells. However, due to the physical constraints, the transverse dimensions of the practical covers should be finite and in the order of antenna size. Therefore, the retrieved results should be considered as an initial value for an optimization process in order to achieve the optimum radiation characteristics.
3.3. Simulated Results
A 5 x 5 array of twisted crosses unit cells is placed above ARSPL antenna with spacing d, as shown in Figure 2(b). The transverse dimensions of the cover and conducting cavity are equal. Numerical simulations performed in a frequency range of 5.5 GHz to 7 GHz show that the optimum value of d is about 26 mm. In this case, the RCP gain of ARSPL antenna with cover approaches 14dB at frequency 5.9 GHz, while the common antenna without cover has a gain of 8.6dB. Theoretically, the maximum gain (or directivity) of an aperture antenna with the same transverse dimensions as ARSPL antenna is 4[pi]A / [[lambda].sup.2] = 14.44dB. Therefore, the gain of ARSPL antenna with CMM cover has almost approached the theoretical limit of antenna gain with the same size and operating frequency. The radiation patterns in the [phi] = 0[degrees] plane at 5.9 GHz for the ARSPL antenna with and without CMM cover are shown in Figure 4. The radiation patterns in [phi] = 0[degrees] and [phi] = 90[degrees] planes are almost the same. Observe that the RCP gain of ARSPL antenna with CMM cover is about 24dB higher than its LCP gain in the boresight direction ([theta] = 0[degrees]). Also, the placement of CMM cover on ARSPL antenna causes the half power beam width (HPBW) to decrease from 87[degrees] to 24[degrees] and the side lobe level (SLL) to increase from -28dB to -18dB.
[FIGURE 3 OMITTED]
[FIGURE 4 OMITTED]
The simulated RCP gain, AR in the boresight direction ([theta] = 0[degrees]), and [S.sub.11] of ARSPL antenna (with feed impedance of 150 [OMEGA]) with and without CMM cover in the frequency range from 5.9 GHz to 6.5 GHz are shown in Figure 5, where the effects of placing CMM cover on the ARSPL antenna with absorbing strip (ABS) are also shown. Observe that the RCP gain of ARSPL antenna with CMM cover is increased by about 3.5-5.4dB and AR and return-loss are considerably improved in this range. Furthermore, the AR of ARSPL antenna with both cover and the absorbing strip is less than 1 dB, which is an excellent property of the CP antenna. However, utilizing an absorbing strip in conducting cavity of ARSPL antenna (and absorption of energy in the cavity) causes some degradation of antenna gain. Further studies show that with increasing the transverse dimensions of cavity, the side lobe levels of radiation patterns are considerably reduced.
4. TWO-ARM ARCHIMEDEAN SPIRAL ANTENNA WITH DENDRITIC FRACTAL CMM COVER
4.1. Dendritic Fractal Cover Design
As mentioned before, the retrieved electromagnetic parameters of the semi-planar CMM structures are only valid for a rather large array consisting of many unit cells, while the sizes of antenna and its cover are finite. To rectify this problem, the miniaturized semi-planar CMM structures having smaller unit cells can be utilized.
[FIGURE 5 OMITTED]
One type of simple fractal geometry that can be utilized to increase the length of wires and miniaturize the structure is the dendritic fractal geometry. This fractal structure is generated by an iterative sequence to the starting simple wire structure. In the first iteration, the top segment of this wire is split at an almost optimized angle, [theta] = 60[degrees]. As the iterative process continues, the end segment of each branch splits into two branches. The unit cell of dendritic fractal CMM structure is shown in Figures 6(a), (b). The lengths of straight sections in any arm of this structure correspond to the ratios of 1 / 2, 1 / 4, 1 / 8, 1 / 16, 1 / 16 and the transverse dimension of aggregate unit cells equal to 15 mm x 15 mm. With planar scaling (in x-y plane) of proposed structure with scale factor 0.6 and simulating in a frequency range of 4 GHz to 10 GHz, the real and imaginary parts of [n.sup.[+ or -]] are calculated and illustrated in Figure 7. With attention to these results, it is expected that the frequency of about 5.9 GHz is appropriate for focusing electromagnetic waves and achieving directive emission.
[FIGURE 6 OMITTED]
[FIGURE 7 OMITTED]
4.2. Simulated Results
A 9 x 9 array of planar scaled dendritic fractal unit cells (with scale factor of 0.6) is placed at a distance d from the ARSPL antenna with cavity dimensions of 81 mm x 81 mm x 7 mm, as shown in Figure 6(c). Numerical simulations executed in the frequency range 5.5 GHz to 6.5 GHz shows that the optimum value of d is about 25.5 mm. It can be seen that the obtained frequency from optimization process (i.e., 5.8 GHz) is very close to the initial value of frequency obtained from the retrieved results. Such a consistency is certainly due to the use of a CMM cover consisting of many unit cells. Theoretically, the maximum gain of an aperture antenna with the same transverse dimensions as ARSPL antenna at frequency of 5.8 GHz is 4[pi]A/[[lambda].sup.2] = 15dB. The radiation patterns in the [phi] = 0[degrees] plane at 5.8 GHz for the ARSPL antenna with and without dendritic fractal CMM cover are shown in Figure 8. Observe that the RCP gain of ARSPL antenna with cover is about 23 dB higher than its LCP gain in the boresight direction ([theta] = 0[degrees]). Also, the HPBW of antenna with cover is about 25[degrees] while the common antenna without cover has a HPBW of about 101[degrees].
[FIGURE 8 OMITTED]
The RCP gain and AR in the boresight direction ([theta] = 0[degrees]), and [S.sub.11] of ARSPL antenna with and without CMM cover in the frequency range of 5.9 GHz to 6.5 GHz are shown in Figure 9. Here, the RCP gain of ARSPL antenna with cover approaches 13.5dB at frequency 5.8 GHz, while the common antenna without cover has a gain of 8dB. Observe that due to the absence of absorbing strip in the metallic cavity, AR of common antenna without cover is higher than 3dB, but with the addition of CMM cover AR is significantly decreased. Also, the RCP gain of antenna with the CMM cover is increased by about 3-6.3dB.
[FIGURE 9 OMITTED]
5. HELICAL ANTENNA WITH TWISTED CROSSES CMM COVER
5.1. Antenna Design
The geometrical configuration of the helical antenna is shown in Figure 10(a). This is a relatively simple non-planar traveling wave type antenna consisting of a conducting wire wound in the form of a screw, usually backed by a ground plane or shaped reflector and driven by an appropriate feed. The most common design is a single wire backed by a ground and fed by a coaxial line. The axial mode of operation occurs when the circumference of helix is in the order of one wavelength. The most important parameters of a helix are the beam width, gain, impedance and axial ratio as given by formulas in Ref.  in terms of N (the number of turns), C (the circumference) and S (the spacing between two turns). In this section, an axial mode helical antenna at the frequency of about 6 GHz with geometrical parameters of N = 5, D = 15.9 mm, S = 11.55 mm, a = 0.5 mm and axial length L = 58 mm is considered.
[FIGURE 10 OMITTED]
5.2. Placement of CMM Cover and Simulated Results
A 5 x 5 array of twisted crosses unit cells is located at a distance L + d from the antenna ground plane with dimensions 75 mm x 75 mm, as shown in Figure 10(b). Numerical simulations performed in the frequency range 5.5 GHz to 6.5 GHz show that the optimized value of d is about 23 mm. The RCP gain of antenna with CMM cover approaches 14.1dB at 6 GHz, while the common antenna without cover has RCP gain of 11.5dB. Note that the maximum gain of an aperture antenna with the same transverse dimension of the proposed antenna is 14.5dB. The radiation patterns in the [phi] = 0[degrees] plane and at frequency of 6 GHz for the helical antenna with and without CMM cover are shown in Figure 11. The radiation patterns of the proposed antenna in the [phi] = 0[degrees] and p = 90[degrees] planes are almost the same. The RCP gain of helical antenna with cover in the boresight direction ([theta] = 0[degrees]) is about 40dB higher than its LCP gain. Also, the HPBW and SLL of helical antenna with cover are 26[degrees] and -13dB, while the common helical antenna without cover has HPBW and SLL of 49[degrees] and -14dB, respectively. AR as a function of [theta], and [S.sub.11] of ARSPL antenna (with the feed impedance of 100 [OMEGA]) with and without CMM cover in the frequency range 5.5 GHz to 6.5 GHz are illustrated in Figure 12. Note that AR of antenna with CMM cover in the boresight direction approaches 0.17dB.
It should be noticed that the dendritic fractal CMM structure proposed in Section 4.1 can be also utilized in this antenna structure.
[FIGURE 11 OMITTED]
[FIGURE 12 OMITTED]
A novel technique based on the chiral metamaterial (CMM) structures for enhancing the gain and improving the axial ratio (AR) of circularly polarized (CP) antenna is presented and investigated by numerical simulations. Two CMM structure were used as covers for planar Archimedean spiral (ARSPL) and non-planar helical antennas. The results show that the gain and AR of antennas can be significantly improved with the addition of the CMM covers in a proper place over the antenna, so that CP antenna gain almost approaches the theoretical limit of antenna gain. Gain of the cavity backed ARSPL antenna with the twisted crosses and the dendritic fractal CMM covers increased by about 5.5dB at 5.9 GHz. Also, the gain of helical antenna with the twisted crosses cover increased by about 2.6dB at 6 GHz. The results show that the best location for placing semi-planar CMM covers is about a half wavelength distance above the CP antenna at frequency of the best radiation characteristics are achieved. Thus, this criterion can be considered to select an initial value for optimization process.
Received 5 November 2011, Accepted 19 December 2011, Scheduled 29 December 2011
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D. Zarifi *, H. Oraizi, and M. Soleimani
Antenna and Microwave Research Laboratory, Iran University of Science and Technology, Tehran 1684613114, Iran
* Corresponding author: Davoud Zarifi (email@example.com).
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|Author:||Zarifi, D.; Oraizi, H.; Soleimani, M.|
|Publication:||Progress In Electromagnetics Research|
|Date:||Jan 1, 2012|
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